Ground-penetrating radar (GPR) systems are powerful tools for nondestructive, noninvasive subsurface detection.1,2 These systems are suitable for measuring the geometric parameters of buried objects,3 locating bars of armor, detecting cavities or breaks inside structures,4 and groundwater detection.5 GPR has widespread application in civil engineering for such tasks as investigating reinforced concrete structures6 and localizing bars of reinforcement in concrete. GPR systems can also be used to determine defects, internal morphology, and lack of homogeneity in materials in civil engineering and preventive characterization of soils and contextual mapping of subsoils for structural safety analysis.7 In the current study, the use of chirp transmission and reception in a frequency-modulated continuous-wave (FMCW) GPR will be examined for defining the mass density of an illuminated ground layer.

Subsurface radar systems have been built using a variety of modulation types depending on the particular requirements of penetration depth, resolution, known target characteristics, software available for data processing, reduction of electromagnetic interference, system size, and cost. The four GPR architectures are pulse wave radar,8,9 continuous-wave (CW) radar, 10 modulated CW radar,11, 12 and synthetic pulse radar. Ground mass density is an important parameter in civil engineering, and the FMCW GPR is a useful tool for evaluating this parameter. This type of radar provides less penetration than a pulsed type radar, but with better resolution. Efforts have been made to improve the detection and evaluation capabilities of GPR systems by developing wideband antennas,5,13 imaging and signal processing algorithms,14, 15 and by improvements in transmitter and receiver circuitry. Figure 1 presents the transmitted waveforms of different radars in one measurement cycle.

Most GPR systems are based on discrete pulse transceivers, although there can be some problems in applying signal processing with this approach. It may be necessary to determine the amplitude-time dependencies of electromagnetic (EM) field components due to wave scattering at a material interface.16 In some cases, the time needed for successful detection may be long and impractical.17

An FMCW GPR system can overcome these difficulties, working in the frequency domain (Fig. 2).

The frequency-domain behavior of an FMCW GPR is shown in Fig. 3. During each period, T, the transmitted frequency is linearly increased to achieve the desired bandwidth, B. During the process of transmitting and receiving, a delay, τ, will occur. This delay is the difference in frequency between transmitted and received signals for the duration of the chirp. It is called the beat frequency and is represented by fB. The transmitter and receiver frequencies, fT and fR, are determined by Eqs. 1 and 2, respectively:

fT = f0 + at (1)
fR = f0 +a (t t ) (2)
where
a = B/T,
B = the bandwidth of the chirp,
and
T = the period of the chirp.

Equation 3 shows that the beat frequency is proportional to the permittivity of the transmission medium,
where
c = the speed of light,
er = the relative permittivity of the medium, and
R = the range (the distance between the transmitter and the receiver) of the GPR.

For civil engineering, one of the most important properties of a medium is its density. This parameter, which is the mass per unit volume of a substance, can be used to determine the compressive strength of road pavement and other materials.18 A material can be thought of as a system of molecules that will react to an incident electric field. The electric polarization P (average electric dipole moment per unit volume) is given by Eq. 419:

P = ?ae0Eloc (4)
where
? = the density of the material's molecular structure,
a = the mean molecular polarizability of the material,
e0 = the permittivity of a vacuum, and
Eloc = the local electric field.

The electric polarization can also be written as
P = (er 1)e0E (5)
where
er = the dielectric constant (relative permittivity) and
E = the applied electric field.

The use of a Lorenzian transformation with Eqs. 4 and 5 yields Eq. 6:
Eloc = E + (P/3e0) = (1/3 )(er + 2)E (6)

The ClausiusMossotti relation can be applied to show that the density of a medium, ?, is proportional to relative permittivity, er:
er 1)/(er + 2 ) = a?/3 (7)

If the mean molecular polarizability and relative permittivity of a medium are known, its density can be found by the ClausiusMossotti relation. By combining Eqs. 3 and 7, it can be shown that the beat frequency at the receiver of an FMCW GPR system is related to the density of the illuminated medium, as in Eq. 8:
fB = 2RB/CT = 0.5 (8)

The permittivity of a material layer, er is proportional to the density of the layer, ?; the EM velocity though the medium depends mainly on the medium's dielectric property, and can be calculated by Eq. 920:
BM = C/( er )0.5 (9)

Changes in the EM propagation velocity result in changes in the time delay, τ, for a signal to travel to the target and back. The density of a material is proportional to the time delay, so that a certain time delay, τ, represents a certain density, ?.

For road and pavement measurements, GPRs can operate over short ranges but must deliver high resolution. An FMCW GPR can provide such performance, and can be improved by means of basic modifications. One of the most important GPR parameters for impacting accuracy is chirp-signal duration. This signal is produced by a voltage-controlled oscillator (VCO) with duration related to the saw-tooth (ramp) duration. For analysis, simulated saw-tooth and chirp signals are shown in Figs. 4(a) and 4(b).The bandwidth of the chirp signal is 900 MHz. When the saw-tooth signal changes from 0 to 10 V, the chirp frequency changes from 1 to 1.9 GHz and is then mixed with a 3.6-GHz local oscillator (LO). The output of the mixer is filtered to achieve a signal that changes from 1.7 to 2.6 GHz.

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Page Title

In the FMCW GPR receiver, part of the transmitted signal is mixed with the received signal. The received signal, of course, is the same as the transmitted signal, but has been attenuated and delayed due to its propagation path, and has gained noise in the process. The delays are equivalent to the density of the medium through which the signals have traveled. The output of the receiver mixer is called the beat signal. It must be filtered and analyzed to determine the properties of the propagation medium.

Figures 5 and 6 present filtered beat signals for a time duration of 10 ns. The frequency of the saw-tooth signal is 100 MHz. Figure 5 presents a beat signal for a time delay of τ1 = 2 ns and a beat period of 5.6 ns. Figure 6 presents a beat signal achieved by τ2 = 4 ns and beat period of 2.7 ns. The beat frequencies are 178 MHz and 370 MHz, respectively, for the two cases in Figs. 5 and 6. Figures 7 and 8 present beat signals for a ramp time duration of 20 ns. The frequency of the sawtooth signal is 50 MHz. Beat frequencies of 91 MHz (T = 11 ns) and 182 MHz (T = 5.5 ns) are achieved for time delays of τ1 = 2 ns and τ2 = 4 ns, respectively in Figs. 7 and 8.

By changing the chirp time duration, the frequency of the beat signal is changed. When the chirp time duration is 30 ns, the frequency of the saw-tooth signal is 33 MHz. Figures 9 and 10 show filtered beat signals for time delay of τ1 = 2 ns and τ2 = 4 ns, respectively. When τ1 = 2 ns, the beat frequency is 62 MHz (T = 16 ns) and when τ2 = 4 ns, the beat frequency is 125 MHz (T = 8 ns).

Data achieved from simulation results and shown in the figures are collected in the table. They can be compared with each other to understand the effects of chirp period on beat frequency. In all cases, the same travel time is assumed from the transmitter to the receiver, at 2 ns. The beat frequency for each chirp duration is listed in the table, so that the difference between beat frequencies equivalent with each time delay is calculated. As should be obvious, when the chirp time duration (T) is smaller or when the ramp frequency is larger, ?fB, it is easier to detect changes in beat signals as a function of material properties. This also results in simpler requirements for the FMCW GPR receiver.

In summary, when the chirp duration is smaller (the ramp frequency is larger), the beat frequency changes on a larger scale, as shown in the table. By small changes in travel time from an FMCW GPR transmitter to receiver, larger changes in beat frequency are achieved. By using smaller chirp durations in these systems, it is possible to achieve greater accuracy even when using a simpler receiver.

REFERENCES

1. Liye Liu, Yi Su, Chunlin Huang and Junjie Mao, "Study about the radiation properties of an antenna for groundpenetrating radar," International Symposium on Microwave, Antenna, Propagation and EMC Technologies for Wireless Communications, Vol. 1, Beijing, China, 2005, pp. 391-394.

2. G. Angiulli, V. Barrile, G.M. Meduri, R. Pucinotti and S. Tringali, "Classing and Extracting Information from Radar Images," Progress In Electromagnetics Research Symposium, Vol. 4 (6), pp. 621-624, 2008.

3. B. A. Yufryakov and Oleg N. Linnikov, "Buried Cylinders Geometric Parameters Measurement by Means of GPR," in Progress In Electromagnetics Research Symposium, Vol. 2 (2), Cambridge, USA, 2006, pp. 187-191.

4. J. Hugenschmidt, J., "Concrete bridge inspection with a mobile GPR system," Construction and Building Materials, Vol. 16, pp. 147-154, April 2002.

5. He Yiwei, Hiroshi Mitsumoto, and Zhongquan Ren, "Echo Extraction Method for a Ground Penetrating Radar," Progress In Electromagnetics Research Symposium, Vol. 3 (5), pp. 701-703, 2007.

6. Bungey, J.H., M.R. Shaw, S.G. Millard and T.C.K. Molyneaux, "Location of steel reinforcement in concrete using ground penetrating radar and neural networks," in International Conference on Structural Faults and Repairs, Vol. 38, London, 2005, pp. 203-212.

7. Angiulli, G., V. Barrile and M. Cacciola, "The GPR Technology on the Seismic Damageability Assessment of Reinforced Concrete Building," in Progress In Electromagnetics Research Symposium, Vol. 1 (3), Hangzhou, China, 2005, pp. 303-307.

8. Lee, J.S., C. Nguyen and T. Scullion, "Impulse Ground Penetrating Radar for Nondestructive Evaluation of Pavements,"in MTT-S International Microwave Symposium Digest, Vol. 2, Seattle, WA, 2002, pp. 1361-1363.

9. Elkhetali, S. I., "Detection of Groundwater by Ground Penetrating Radar," in Progress In Electromagnetics Research Symposium, Vol. 2 (3), Cambridge, USA, 2006, pp. 251-255.

10. Grazzini, G., M. Pieraccini, F. Parrini and C. Atzeni, "A Clutter Canceller for Continuous Wave GPR," in 4th International Workshop on Advanced Ground Penetrating Radar, Naples, Italy, 2007, p. 212-216.

11. van den Bosch, I., S. Lambot, M. Acheroy, I. Huynen and P. Druyts, "Accurate and Efficient Modeling of Monostatic GPR Signal of Dielectric Targets Buried in Stratified Media," in Progress In Electromagnetics Research Symposium, Vol. 1 (2), Hangzhou, China, 2005, pp. 251-255.

12. Boukari, B., E. Moldovan, S. Affes, K. Wu, R.G. Bosisio and S.O. Tatu, "A heterodyne six-port FMCW radar sensor architecture based on beat signal phase slope techniques," Progress In Electromagnetics Research (PIER), Vol. 93, pp. 307-322, 2009.

13. Atteia, G.E., A.A. Shaalan and K.F.A. Hussein, "Wideband Partially Covered Bowtie Antenna for Ground-Penetrating- Radars," Progress In Electromagnetics Research, Vol. 71, p. 211-226, 2007.

14. Hao Chen, Renbiao Wu, Jiaxue Liu and Zhiyong Han, "GPR Migration Imaging Algorithm Based on NUFFT," Progress In Electromagnetics Research Symposium, Vol. 6 (1), pp. 16-20, 2010.

15. van Genderen, P. and I. Nicolaescu, "Imaging of stepped frequency continuous wave GPR data using the Yule-Walker parametric method," in European Radar Conference, Paris, France, 2005, pp. 77-80.

16. Varyanitza-Roshchupkina, L.A. and G.P. Pochanin, "Pulse electromagnetic wave scattering by plane dielectric interface," in 4th International Conference on Ultrawideband and Ultrashort Impulse Signals, Sevastopol, Ukraine, 2008, pp. 241-243.

17. Oguz, U. and L. Gurel, "FDTD Simulations of Multiple GPR Systems," in IEEE Antennas and Propagation Society International Symposium, Ankara, Turkey, 2003, pp. 764-767.

18. R. S. A. Abdullah, H. Z. bin Mohd Shafri, and M. Bin Roslee, "Data Analysis of Road Pavement Density Measurements Using Ground Penetrating Radar (GPR)," in International Conference on Computer and Communication Engineering, Kuala Lumpur, Malaysia, 2008, pp. 732-737.

19. Y. Liu and P.H. Daum, "Relationship of refractive index to mass density and self-consistency," Aerosol Science, Vol. 39, pp. 974-986, 2008.

20. Yong-Hui Zhao, Xiang-Dong Hu and Guo-Qiang Zhao, "Experiment on Artificial Frozen Soil Boundary GPR Detection During Cross-passage Construction in Tunnels," in Progress In Electromagnetics Research Symposium, Vol. 1 (3), Hangzhou, China, 2005, pp. 354-358.